Color television



March 3, 1959 J. w. wl-:NTwoRTH 2,875,347

COLOR TELEVISION Filed 1:96. 4. 195s 'z sheets-sheet 1 March 3, 1959 J. W. WENTWORTH` 2,876,347

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COLOR TELEVISION Filed Dec. 4, 195s '7 sheets-sheet s INVEN TOR.- da/w W Win/fwaxrf/ TTORNEY naze 5 2-. ql k* HU V m M mm Ty l M H i 9 9 l March 3, 1959 Filed Dec. 4, 1953 J. W. WENTWORTH COLOR TELEVISION 7 sheets-sheet 4 TTORNE Y March 3, 1959 J. w. wENTwoRTH 2,876,347

COLOR TELEVISION Filed Dec. 4, 1953 7 Sheets-Sheet 5 1...... .lll

March 3, 1959 J. w. wENTwoRTH 2,876,347 Y COLOR TELEVISION FiledI Dec. 4, 1953 7 Sheets-Sheet 6 kmuvk N TTORNEY mvo W Q M llallsm .sul JW 1 March 3, 1959 J. w.'wENTwoRTH l 2,876,347

COLOR TELEVISION Filed Dec. 4. 1955 7 Sheets-Sheet 7 ATTORNEY United States Paten-t O COLOR TELEVISION John W. Wentworth, Haddonteld, N. I., assignor to Radio vCorporation of America, a corporation of Delaware Application December-1,1953, Serial No. 396,170

9 Claims. (Cl. Z50- 27) This invention relates to test apparatus for color tele-- vision receivers and, particularly, to apparatus for usein testing the phase alignment of the subcarrier demodulator circuits and the gain adjustment of the matriiringv circuits employed in receivers and monitors for convert-Y ing the received color signals to a form suitable for image-reproducing purposes.

In accordance with the presently proposed standards' ofthe National Television System Committee (NTSC), the signal which is transmitted consists of a luminance signal and one or more so-called color difference signals. The luminance signalis made up of predetermined proportions of the signals representinga plurality, such as three selected component colors of a subject. The color difference signals are of` a character such that, Vwhen each is combined 'with the luminance signal, there is produced a signal representative of one of the selected component subject colors and which may be employed in this. form for image-reproducing purposes.

.The color difference signals are transmitted on avsubcarrier wave having a frequency which is at the relatively high end of the frequency -band including theluminance signal. The subcarrier Wave has a frequency which is a large odd multiple of one half of the horizontal or line' scanning frequency. By this means, kthe energy concentrations in the side bands of the color. subcarrier Wave. are interleaved with the discrete energy concentrations of the luminance signal. In View o-f the fact thatv all three of the colorsrare represented inthe luminance signal, itis `necessary to transmitonly two color dilerencei signals. Inthis case, ata receiver, the third color differ. 'ence signal may be derived in a suitable manner byV prop-v er combination of the twov transmitted color difference lsignals-and the luminance signal.

In transmitting the color diiference signals, it is the practice to modulatethem respectively on two quadrature phases of the subcarrier wave. Within the frequency range in which both side bands of 'the color subcarrier wave are transmitted, there is no distortion .of the color difference signals. However, since the color subcarrier wave has a frequency which is in the upper region of the. pass rband of the communication channel, some of the higher color difference modulating signals are transmitted in only one of the color subcarrier wave side bands.' In this single side band region, therefore, it is the practice to transmit only a single color difference signal in order to avoid signal distortion.,

Generally considered, any two color dilference signals may be transmitted by modulating quadrature phases ofV the subcarrier wave. It is desirablehowever, that the subcarrier wave modulating signals be chosenin suchv aV way as to provide the most acceptable image reproduction when only a singlecolor difference signal is trans,.- mitted in the single side band region. It has been found that the color difference signals themselves do not provide the best kind of image reproduction. It,ther efore; has been the practice recently to derive two signals (designated I and Q) by which to modulate the quadrature:

2,875,347 Patented Mar. 3, 1959 phases of the subcarrier wave, which signals are combinations of two of the color difference signals. Accordingly, at a receiver the color dilerence signals forlproper combination with the luminance-signal must be derived from the subcarrier wave modulating signals. For this purpose, a converter isfrequired. Suchia'converter has been called, because of its character, a matrixing circuit. In the present usage, it will bev understood that amatrixing circuit is. electroniclapparatus:for additively. and/orsubtractively combining -signal voltages Ito change them from one form to another. f

By reason of the fact .that thel I and Q signals are not present in an identifiable form in-a picture signal, since such a signal is acontinuously varying-Vector sum ofthe I and Q components; it is-impra'cticable to at tempt to test the phase alignment-of a receiver through the use offa transmitted broadcast signal. Hence, it is a primary object-of the present invention to provide means for synthetically producing subcarrier frequency signals ofthe l and Q phase whereby the phasinggof the corresponding demodulators in a color television receiverl may be checked in a simple, yet quite accurate manner.

Moreover, since the converter or matrix circuitsfreferred vto above must derive the color difference signals. accurately from the ldemodulated I and ,Q signals 1nA order for proper color reproduction to be realized, it is necessary to alord. a check on 'the matrix itself. Thus,`

it is .another object of this invention to provide means for producingaccurate indications of the manner of opera-1y tion'lof the'color difference signal derivingcircuits" of a:

receiver matrix arrangement.

In general, thetest signal generator of the 'present in-v vention comprises means for producing, Awithin a standard television line interval, a-Yplurality of.burstsof color subcarrier wave frequency, each burst having a predetermined phase with Yrespect to a' reference phase such that the bursts serve as a synthetic signal by which the state ofv the receiver circuits phase alignment may be readily and'visually determined. The rst such burstvin'a television line interval..(which may, for example, be M5750; sec.in duration.) is so chosen as the -phasewith respect` to the other. bursts` that, at selected points inthe receiver, certainof the bursts produce.afpredeterminedlevel of instantaneousfvoltagein the case ofa properly aligned receiver. More specifically, aswill appear hereinafter, the several 4bursts mayV be so related in phaseat the output of the signal generator that the proper indication atthe several points checked is zero, thereby facilitating a rapid determination of phase alignment of the receiver-circuits. Since, as is understood, proper operation ofthe receiver color reference oscillator requiressynchronization thereof at frequent intervals normally corresponding to television line rate, the signal generator includes means forr producing a signal for synchronizing the receiver oscillato'r.

While the test generator of the present invention is capable ofaiording4 all of the. test signals described in general terms above, it is relatively simple and inexpen sive kwhen compared to the valuable assistance which it renders in the alignment and servicingfof color televisionV tions representing vthe relationship-of thecolor difference signals and the color subcarrierwave modulating signals in a=system with which the Vpresent invention may be advantageously employed;

Fig. 2 is a block diagram of a4 proposed, typical type of 3 Y color television receiver to which the test signal of this invention may be applied in checking phase alignment;

Fig. 3 illustrates curves indicating the frequency response of a receiver such as that of Fig. 2;

Fig. 4 is a block diagram of apparatus in accordance with the present invention;

Fig. 5 illustrates a signal which the present invention is capable of producing;

Figs. 6-10 illustrate a schematic circuit diagram of a` complete operative embodiment of the apparatus shown diagrammatically in Fig. v4;

Fig. 11 is a vector diagram to be referred to infra; and

Fig. 12 is a diagram of the waveforms of a correctly aligned color receiver.

In order that the utility of theinstant invention may be fully understood and appreciated, there follows a somewhat detailed description of a typical color television receiver capable of reproducing a color television image from the signal of the proposed NTSC type.

Reference first will be made to Fig. l of the drawings for a general description of the color television signalling system in which the present invention is embodied. This .figure includes a vector diagram in which the respective red, blue and green color difference signals are represented by the vectors (R-Y), (B-Y) and (G-Y). It will be understood that this vector diagram represents only the angular relationship between the various signals referred to. The illustrated lengths of the vectors is insignicant, since these lengths change with-the diterent color content of the subject represented by the signals. Also, it will be understood that, with respect to the color difference signals (R-Y), (B-Y) and (G-Y), the representative vectors indicate the angular relationship between such signals, if, in fact, the color subcarrier wave were modulated directly by the color difference signals. In this system, however, the color subcarrier wave is not directly modulated by these color dierence signals, so that the various representative color difference signals are shown merely for reference purposes. In this connection, it is noted that the burst signal vector is 180 out of phase with the blue color difference signal (B-Y). The burst signal is employed in a manner to be described more fully subsequently to eiect synchronous operation of the color signalling apparatus at the transmitter and receiver.v

It also may be noted from the vector diagram of Fig. 1 that the red color dilerence signal (Rm-Y) leadsA in phase the blue color difference signal (B-Y) by 90. Accordingly, the' burst signal leads the: red color diierence signal (R-Y) by 90. Furthermore, in accordance with the presently proposed NTSC standards, the system operates by the Vmodulation of the color subcarrier wave directly by two signals designated respectively as the I and Q signals. From the vector diagram, it may be seen that the I signal leads the Q signal in phase by90". Also, the I and Q signals lead in phase, respectively, the red color difference signal (R-Y) and the blue color difference signal (B-Y) by 33.

In the remaining portion of Fig. 1, the dilferent amplitude relationships between the various vectors representing signals shown in this figure are given by the equations in which the quantities referred to are signal voltages. In order to present the relationships between the various signal voltages as clearly as possible, it will be understood that the various letters and quantities represented by letters grouped together in brackets or parenthesis represent the signal voltages indicated by the different letters referring to the diiferent color and the luminance signals. As indicated in Equation l, the luminance signal Y is made up of the algebraic sum of the specified quantities of the green, red and blue signals G, R and B respectively representing light of these colors derived from the subject. Also, in Equations 2, 3 and 4 the various color dilerence signalsv I and Q subcarrier wave modulating signals.

`diagram of this figure.

(It-Y.) (B-Y) and (G-Y) are given in terms of the color signals representing the subject. The l and Q" subcarrier wave modulating'signals are given in Equations 5 and 6, respectively, in terms of the diierent color signals representing the subject. In addition, the color difference signals (R-Y), (B-Y) and (G-Y} are expressed in Equations 7, 8 and 9 in terms of the These latter relationships, particularly with reference to the signs of the I and Q signals, may be seen to correspond with the relationships shown in the vector The denominators of the lefthand terms of these equations are indicative of the amplification which the algebraic sums of the related I and Q modulating signals should be given in order to produce the proper color difference signals for combination with the luminance signal to develop the proper color signal for image-reproducing purposes.

Reference now will be made to Fig. 2 for a general description of a representative type of color television signal-receiving and image-reproducing apparatus in which the present invention is embodied. A carrier wave on which the composite color television signal is modulated is intercepted by an antenna 11 which is coupled in a conventional manner to a television receiver 12. It Will be understood that this receiver includes such conventional apparatus as carrier Wave ampliers, at both radio and intermediate frequencies, a frequency converter and a second or signal detector. Accordingly, it will be understood that there is derived from the signal detector in the output circuit of the receiver 12 a composite intelligence signal having both video and synchronizing signal components. The video signal component is a composite luminance and chrominance signal in accordance with the present NTSC proposed standards, while the synchronizing signal component includes the conventional horizontal and vertical synchronizing signals by which the deliection apparatus is controlled and, in addition, a color synchronizing signal.

The composite video signal component is impressed upon a video signal amplifier 13. The deflection synchronizing signal is impressed upon the deflection circuit apparatus 14. The color synchronizing signal is impressed upon apparatus by which to control the frequency and phase of a reference frequency oscillator 15.

The video amplifier 13 may be conventional apparatus including one or more stages of video signal ampliiication and having a comparatively Wide pass band of the order of 5 megacycles. The deiiection circuits'14 also may be conventional and include the usual sync signal separators, automatic frequency control apparatus and sweep frequency generators to produce substantially sawtooth waves respectively at horizontal and vertical detiection frequencies. The reference frequency oscillator is one which is capable of oscillating with relatively good stability to produce a reference frequency of the order of 3.58 megacycles. More specifically, in accordance with the presently proposed NTSC standards, the frequency of this oscillator is 3.579545 megacycles which is the 455th harmonic of one-half of the line or horizontal deflection frequency when the latter is defined as the 572nd subharmonic of 4.5 mc. (the standard spacing between picture and sound carriers in a television broadcast channel).

This composite intelligence signal, when directed into the Various circuits described, is effective to control the operation of an image-reproducing device such as a tricolor kinescope 16. Such a kinescope is or may be of the same general type as that described in a paper by H. B. Law entitled A Three-Gun Shadow-Mask Color Kinescope and published in the Proceedings of the l. R. E., vol 39, No. 10, October, 1951 at page 1186. Such a color kinescope also forms the subject matter of U. S. Patent No. 2,595,548 granted May 6, 1952 to A. C. Schroeder and entitled Picture Reproducing Apparatus."

The. video, signals, ,after 1.,@ neze'sary .progressing .in a

Jing time delay apparatus 18`and indicated as conveying the Y signal. The purpose of the delay apparatus is Yto compensate for the inherent delay in some of the .chrominance channel apparatus. V'The composite video .signal is also impressed upon a chrominance signal channel through a band pass filter 19 `which passes vvideo signals in the range extending approximately from 2 to 4 megacycles. 'The output` of the band pass filter 19 is limpressedrespectively upon Q andT signal demodvulators 2t) and 21. These demodulators are of a synhronous type in which the color subcarrier wave, to-

rgether with its sidebands, are mixed with different phases of the reference frequency derived from the oscillator 15.

inasmuch as the Q and I signals are modulated upon the .subcarrier wave in a quadrature phase relationship, the Q and I signal demodulators 20 and 21 have impressed thereon quadrature phases of the reference v`frequency wave.

These quadraturephases are derived from a conventional phase splitter22 coupled to the output of the reference frequency oscillator 15.

As a result of the synchronous demodulation by the Q and I signal demodulators 20 and 21 respectively,

Ythere .are produced in the output circuits thereof the Q and I signals aslindicated. The Q signal derived from `the demodulator 20 is passed through a low `pass filter 23 having a pass band of approximately 50() `kilocycles. lIn a somewhat similar manner, the I signal derived from the output I signal demodulator 21 is passed through a low pass filter 24 having a pass band of approximately 1.5 megacycles.

The-Q and I signals produced in the output circuits of the low pass filters 23 and 24, respectively, are impressed upon a matrixing circuit 25 by means of which they are converted into the green, blue and red color difference signals (G-Y), (B-Y) and l(R-Y), respectively. In the circuit coupling the low pass filter 24 to the, matrixing circuit 25, there is included a delay apparatus 26 having for its purpose the introduction of a vsuitable delay in the I signals -to compensate for the delay produced in the Q signals bythe inherent operation of the low pass filter 23.

yThe green, vblue and red color difference signals (G-Y), (B-Y) and (R-Y), respectively, derived from vthe matrxing circuit'25 are impressed upon a signal combiner 27. Also, the Y or luminance signal derived from the delay apparatus 18 is impressed upon the signal combiner. This apparatus functions tocombine the luminance or Y signal with the green, blue and red color difference signals (G-Y), (B-Y) and (R-Y) in such a manner as to produce in its output circuit the green, blue and red signals G, Band R respectively representing the component colors of the image to be reproduced. These signals are impressed upon the electron beam intensity control electrodes of the tri-color kinescope v16 in a conventional manner.

The synchronizing of the reference frequency oscillator 15 with a similar color subcarrier wave oscillator at the transmitter may be effected by transmitting a burst `to approximately 1.1 megacycles.

.gamen 6 tion .in the RCA Color Television System published by `the`Radio`Corporaton of America, February,v 1950.*3'11`he l'receiver apparatus of such a systemis disclosed particularly in Fig. 9 of that paper, Such a s'ynchroniz'vinggsystem also forms the subject matter of a copending'U. S. patentvapplication of A. V. ABedford,-Serial No.-143,'80'0, filed February 11,1950, now Patent No. 2,728,812, issued December 27, 1955, and Ytitledsynchronizing Apparatus.

The characteristics of thev low pass filters in the I and Q channels are indicated more particularly in the curves ofnFig. 3, to which reference now will be made. The curve 31 represents the frequency response characteristic of the low pass filter 23 vvin the Q 'signal channel. Here it is to be notedthat the responseis substantially fiat out-to a frequency which is slightly less than 500 kilocycles and is substantially zero at a Vfrequency of approximately 600 kilocycles.

In a like manner, the curve 32 represents the frequency response characteristic of the low pass filter 24 in the I signal channel. The overall frequency response in this channel is seen Vto be somewhat greater and is approximately 1.5 megacycles. Up to a frequency of approximately 425 kilocycles the response is substantially constant at a level which is approximately one-half of the level of the response in a higher frequency range up The response in the Q signal channel low pass filter 23 as represented by the curve 31 also is at about thevsarne level as that-of the response by the low pass filter 24 in the I signal channel as represented bythe curve 32 upto-a frequency vof approximately 425 kilocycles. The reason for this `amplitude relationship is that in the frequency range up to approximately 500 kilocycles, .when'both I and Q signals are presennthe total energy, represented byA these two signals should be approximately vthev same as the energy of theTsignal in the higher frequency range up -to approximately 1.5 megacycles -within which the Q is not present.

Referring nowv to Fig. v4, `there is shown a block diagram of a-color test signal generator .in accordance with the present invention. Since, as has 'been stated, it is necessary to provide horizontal synchronizing pulses to the lreceiver under test in order that its color burst gating and synchronizing circuits may performproperly, the lapparatus of Fig. 4 includes async pulse oscillator 34'which may, as will -be seen, comprise a free running or astable multivibrator producing substantially rectangular pulses 36 having a repetition rate-of nominally 15.75 kc. for application to a multivibrator 38 whose output pulses 40 are applied, in turn, to a s cale-of-two divider 42 and (R-Y) gating circuit 44. The output of the divider multivibrator 4Z is, in turn, -employed to trigger multivibrator MV2 indicated by block 46 at a rate of 7.875 kc. (or half of the normal television line repetition rate). Multivibrator.46, in turn, triggers multivibrator MVS (block 48) whose output ltriggers the succeeding multivibrator MV4 indicated by block 50. The output pulse of the last-mentioned multivibrator triggers the final multivibrator MV5 shown diagrammatically by block 52. Each of multivibrators MV2,` MV3, MV4 and MV5 provides a gating pulse to its associatedgate circuit, namely, the I gate 54, the (G-Y) gate rv56, the Q gater58 and the (B-Y) gate 60. `A color subcarrier frequency wave is produced by a highly stable crystal oscillator 62 Whose output, after amplification by buffer arnplifier 64, is applied to the gate circuits after various amounts of electrical delay. More specifically, the `subcarrier frequency wave of, for example, 3.58 megacycles is applied directly to the I gate tube 54. 'The s ubcarrier wave is delayed` 33 as by means of an accurately -cut cable 66 and applied to the (YR-Y) gate 44. The

is applied to the Q gate. A final delay of 33 is introduced by delay means 72 and the resultant wave is applied to the (B-Y) gate.

From the foregoing, it will be seen that the (l-Y) gate tube 44 is keyed or pulsed on once during each television line interval, immediately following the synchronizing pulse 36. On the other hand, the 1, (G-Y), Q and (1R-Y) gates are pulsed on by their associated multivibrators 46, 48, 50 and S2, respectively, only during alternate television line intervals. The output of each of the gate circuits is applied to a common band pass lilter 74 whose function is that of removing undesired gating disturbances, the output of filter 74 being then applied to an adder circuit 76 which combines the outputs of the gate circuits with the sync pulses derived from oscillator 34. The output of adder 76 is then amplified by suitable means indicated by block 78 so that the composite test signal waveform produced by the apparatus is available at output terminal 80. An

additional output terminal 82 coupled to the sync pulse oscillator 34 has available the sync pulses 36 for purposes to be described hereinafter.

In the operation of the apparatus of Fig. 4, the output wave form available at terminal 80 has the waveshape indicated in Fig. 5. As will be understood from the foregoing description of the block diagram of Fig. 4, its output waveform is as follows: At the beginning of each television line interval, there occurs a horizontal synchronizing pulse 36 followed by the burst produced by the (R-Y) gate of Fig. 4. By reason of the fact that multivibrators 48, 50 and 52 are triggered at only half the frequency as multivibrator 38, their associated gating tubes are activated only during alternate television intervals. Thus, for purposes of illustration, television line l in Fig. 5 is shown as also including the I burst, the (G-Y) burst, the Q burst and the (B-Y) burst. Assuming, merely for purposes of having a convenient reference, that the (R-Y) burst is considered as occurring at as indicated in Fig. S, each of the additional bursts which occur during that televisionrline interval will have a specific phase with respect to the (R-Y) burst as determined by the amount of delay introduced by the various portions of the delay line of Fig. 4. Hence, the l burst in Fig. will lead the (R-Y) burst by 33. Simi- Alarly, the (G-Y) burst will lag the (I2-Y) burst by 34.3. The Q burst will lag behind the (RY) burst by 57 and the (B-Y) burst Will lag the (l-Y) burst by 90". During television line (2) of Fig. 5, the only subcarrier frequency burst which is present is the (R-Y) burst. The next television line interval, only a portion of which is shown in Fig. 5, will include all live bursts, as explained supra.

It should be noted at this point that in accordance with the conventional operation of a color television receiver of the type described in connection with Fig. 2, the color reference oscillator in the receiver is maintained in proper synchronisin with the subcarrier wave generator at the transmitter by means of a burst of reference phase which is transmitted immediately following each horizontal synchronizing pulse. While not shown in Fig. 2, such receivers normally have means including a source of horizontal frequency pulses for gating the color synchronizing bursts, out of the composite received signal which bursts, after separation, are then applied to a frequency control unit for the local color reference oscillator whereby to maintain the oscillator in proper phase with the transmitter. Thus, depending upon the phase of the color synchronizing burst which follows the synchronizing pulse, the local color reference oscillator will produce a subcarrier frequency wave having a particular phase with respect to the received synchronizing bursts. Since the ,phase angles of the last four bursts shown during television line (l) of Fig. 5 are meaningful (Ii-Y) burst, this fact should be borne in mind during only insofar as they refer to the phase of the rst or 8 the later portions of this specication wherein the use of the apparatus disclosed herein will be described.

Before leaving Fig. 4, however, it may be noted that a switch S at the input of buffer amplifier 64 may be used to switch from the crystal oscillator 62 to some suitable external source of 3.58 megacycle wave in such cases as might make it desirable to employ an external subcarrier source.

A complete and operative embodiment of the present invention, which is shown diagrammatically by the block diagram of Fig. 4, is disclosed by Figs. 6-10. More specifically, as will be appreciated from an inspection of the drawing, Fig. I6 includes the sync pulse oscillator 34 and multivibrator 38 as well as multivibrator 42. ln a similar manner, Figs. 7 through 10 disclose additional portions of the complete test signal generator of Fig. 4.

Referring to Fig. 6, the sync pulse oscillator shown within dotted line box 34 comprises an astable or free running multivibrator illustrated as being of the type described and claimed in the co-pending U. S. application of Arch C. Luther, S. N. 377,925, tiled September l, 1953. Briefly, the operation of the sync pulse oscillator 34 differs from conventional astable multivibrators in several respects, as will appear from its description. The multivibrator comprises two vacuum tubes V1 and V11,- The cathode of tube V1,l is connected to ground, while the cathode of tube V1 is connected to ground through a large resistor 86 bypassed by a storage capacitor 88. The R-C circuit in the cathode of tube V1 has a large time constant relative to the period of the multivibrator so that the cathode of that tube is maintained at a relatively small potential, whereby a moderate voltage transition from the plate of tube V13, to the grid of tube V1 is suflicient to render the latter tube conductive. Connected between the plate of tube V1 and a source of positive potential (+240 volts) is a tuned circuit comprising inductance 99 and shunt capacitor 92, a crystal diode being connected in parallel with the resonant circuit which elements 92 and 9i) form. The diode 94 serves to cut off or clip the positive half cycles of oscillation produced by the resonant circuit. The plate of tube V1 is, as shown, coupled to the grid of tube V111 via a time constant circuit comprising capacitor 96 and resistor 98 whose free end is connected to the cathode of tube V1. At the end of the timing cycle determined by capacitor 96 and resistor 98, tube V11, is rendered conductive and a surge of plate current passes from the +260 volt terminal through the resonant circuit and through tube V1a to ground. This surge of plate current starts an oscillation in the ringing circuit having a period determined by the values of inductance and capacitor 92. The initial half cycle of such oscillation is a negative-going wave, the following positive-going half cycle of oscillation being prevented by conduction through the damping diode 94. Hence, after a negative half cycle of oscillation in the ringing circuit, the potential on the grid of tube V1 and on the plate of tube V11, returns to +260 volts. Also during this negative half cycle, tube V1 is cut off and tube V1., is conductive. Capacitor -88 maintains the cathode of tube V1 at a constant potential, as will be understood. At the end of the half cycle of oscillation in the ringing circuit, the grid of tube V1 returns to approximately 260 volts and that tube begins to conduct. In the meantime, while tube V1 is cut off, timing capacitor 96 was recharged so that after tube V1 becomes conductive a new timing cycle is initiated. It is thus apparent that the ringing circuit 90, 92 determines the period of time that tube V1 is cut olf and the timing circuit 96, 98 determines the time during which tube V1,l is cut off. As described in the above-cited Luther application, the advantages of the oscillator in the form shown are that it produces an output pulse 36 at the plate of tube V1 which has a rather steep trailing edge and which occurs at an extremely stable reptition rate. Pulse 36 is thus available at output terminal H and is also coupled via capacitor 100 aereas? to an amplifier 102. 'Ihe negative-going pulse 36' at the output'v of amplifier 102 is` differentiated by means of capacitor 104 and resistor 106 to produce alternate negative and positive spikes 36a and 36b, respectively. The positive spike 36b is passed by diode 108 and is applied as a trigger pulse to the control grid of the rst tube of multivibrator 38. Multivibrator 38, is as shown, a conventional form of cathode coupled multivibrator such as is described in volume 19 of the MIT Radiation Laboratories Series, entitled Waveforms, chapter 5, page 170.

As determined by its time constant circuits, multivibrator 38, which is of the monostable variety, has a repetition-rate of nominally 15.75 kc (or, in other words, television line rate). Taken from the plate load circuit of the second tube of multivibrator 38 is a positive-going pulse of predetermined duration which is available at terminal J and which, as will appear, is applied to the (R-Y) gate tube 44 (Fig. 4). A negative pulse taken from the cathode of the multivibrator 38 is, in turn, coupled via capacitor 110 and 112 to the control grids of the tubes forming multivibrator 42. This last-named multivibrator is of the bi-stable type described generally in chaper of the above-cited Waveforms (pages 164- 166) and serves to divide the input pulse frequency by a factor of two, the rising, or trailing, edge of the pulse from the cathode of MV1 serving as the trigger. Thus,A

the output of multivibrator 42, which comprises a square wave having a repetition rate of 7.875 kc., is available at terminal K for application to multivibrator MVZ shown within dotted line box 46 of Fig. 7;

Referring to Fig. 7, terminal K is intended to be coupled to terminal K of Fig. 6 so that there will be applied to the control grid of the left hand tube forming multivibrator MV2 through an RC network that differentiates slightly a positive-going pulse corresponding to the rising edge ofthe 7.875 kc. square wave. This pulse is designed to trigger that multivibrator which is, incidentally, of the monostable variety. That is, for each input trigger to MV1,` there is made available one output pulse. Moreover, by reason of the fact that multivibrator MV2 is triggered by a pulse from multivibrator 42, it Will be appreciated that multivibrator MVZ will produce an output pulse following, in time, the pulse produced by multivibrator MV1 shown in block 38 of Fig. 6. Multivibrator MV1,Y Vis substantially identical to multivibrator MV1 of Fig. 6, Vwith the exception of a different cathode resistor which is necessitated by the slightly different character of theV trigger pulse'applied to multivibrator MVg. At terminal L, which is connected to a point in the plate load circuit of the second tube in multivibrator MV2, there is available a positive pulse. A negative pulse appearing at the cathode of MVZ is differentiated by capacitor 109 and resistor 11711 to produce a positive trigger pulse corresponding'to' the trailing edge of the pulse at terminal N. The negative spike occurring at the leading edge of the pulse from multivibrator MV2 has no effect on the following multivibrator MVS. The triggering pulses are coupled from terminal N to the input of multivibrator MV3 shown in dotted line block 48. Multivibrators MV3, MV1 (box`50) and multivibrator MV5, (box 52) are all substantially identical to each other so that the values of the various elements in the last two multivibrators may be exactly equal to the corresponding components of multivibrator MV3. The operation of multivibrator MVS, MV.1 and MV5, however, is substantially the same as that of multivibrator MVZ. Thus, it will be understood that each of multivibrators MV2, MV3, MV4 and MV5 will be triggered by the multivibrator preceding it so that their output pulses will occur successively in time. Thus, a positive gating pulse will be available at each of output terminals P, S and T just as was described in connection with terminals I and L for multivibrators MV1 and MVZ, respectively.

Fig'. 8 includes a schematic' showing of the circuits of the: iivegatetubesindicated diagrammatically in Fig. 4.

These gate circuits vare shown in Fig. 8 within the dotted line Vboxes 44, 54, 56, 5S and 60. Since all of the five gate circuits are substantially identical Vto each other, onlythe (R-Y) gate 44 need be described in detail.v Gate 44 comprises a pentode 118 whose suppressorgrid is supplied at terminal 1' with the positive pulses from terminal J of multivibrator MV1. The screen grid of `the tube 118 is connected through dropping resistor 120 to a source of positive potential indicated as +260 volts and is bypassed to ground through a capacitor 122. The cathode of tube 118 includes a resistor 124 and shunt capacitor 126 for self-'biasing purposes. Resistor 124A provides additional bias for the suppressor grid by means of current drawn through tube 118- and also through the bleeder consisting of resistors 120, 120A and 124. Coupled to the control grid of gate tube 118 via coupling capacitor 128 and grid resistor 130 is an. input terminal U to which is applied, in a manner to be described, a subcarrier frequency wave of specific phase with respect to a reference. The anode of gate tube 118 is connected to a lead 132 which, as may be seen, is 'common to the anodes of the other four gating. tubes shown within blocks 54, 56, 58 and 60.

In the operation of gating circuit 44, assuming a subcarrier wave of specified phase as being applied to its control grid, the tube will not conduct until there is applied, via terminals J" and .l', to its suppressor grid a positive gating pulse from multivibrator MV1 (Fig. 6). During the occurrence of such a positive pulse on its suppressor grid, however, tu'be 118 will conduct so that its output will constitute a discrete burst of subcarrier wave frequency of predetermined phase. The other gating circuits shown in dotted line boxes 54, 56,` 58 and 60 are not described separately. It should, however, be noted that the anode of each of those gating. tubes is also connected to lead 132. Additionally, it may be seen that gate circuit 54 includes an input terminal L for connection to terminal L Aat the output of multivibrator MVZ and that. each of the other gating` circuitsS, 58 and 60 includes an input terminalbearing a reference character having a prime notation but corresponding to an output terminal of the associated multi vibrator of Fig. 7. In other words, terminals E, L

and .P from gate circuits 56, 58 and 60 are intende-dv for connection to output terminals"l, S and T of l multivibrators MV3, MV4 and MV5, respectively, of Fig.

7. While terminals L, S, T and P provide the gating pulses to their corresponding gate tubes, terminals `V, W, X and Z constitute the input ter-V minals to gates 54, 56, 58 and 60, respectively, to which:

areapplied the differently phased subcarrier waves.- Lead 132 terminates at the left hand side of Fig. 8 in terminal 132:1 which is, in practice, connected to a corresponding Yterminal 132b in Fig. l0, to be described.7 Prior to describing the apparatus by which the successive bursts from the several gating circuits are added to each other and' to the horizontal synchronizing pulses,- there will. be given a description of the oscillator andv delay line for providing" the several phases of subcarrier frequency. Referring, therefore, to Fig. 9, there is shown Within dotted line box 136 a conventionalform of oscillator tube 138 whose signal input terminals are adapted to be connected via switch S1 either to the crystal tank. circuit 140 or to the terminal labeled External Subcarrier'lnput, namely, terminal 142.V In the position of the switch S1 as shown, the crystalA ringing circuit 140 is connected in circuit with tube'138 in order to form,

togetherl with the tuned circuit 144 which is in series the output of tube 138 is coupled via lead 146 to the` control grid of a conventional buffer amplifier 148 whose output is inductively coupled by transformer 150 to input terminal 152 of the several sections of delay line indicated within dotted line boxes 66, 68, 'itl and 72. The subcarrier wave is applied, without delay, via lead 154 to terminal V which is intended to be connected to terminal V of the l gate tube 54. Each of the delay line sections 66-72 may, for example, comprise an accurately cut section of a co-axial cable whose delay characteristics have been accurately calibrated per unit length. Thus, after having been delayed 33, the subcarrier frequency wave at terminal is applied to terminal U at the input of the (R-Y) gate circuit 44. After a further delay of 34.3, the subcarrier frequency wave is applied via terminals W' and W to the input of the (G-Y) gate circuit 56. Delay section 70 introduces an additional delay of 22.7"v and its output wave is coupled via terminals and X to the Q gate circuit 58. After an additional delay of 33 which is introduced by the cable section within box 72 and which terminates in a resistor which may be nominally 73 ohms in value, the subcarrier frequency wave is coupled via terminals Z and Z to the (B-Y) gate 60. While the value of the characteristic terminating resistance 160 has been said to be nominally 73 ohms, it should be understood that its value may be reduced, for example, if necessary, to compensate for capacity eiects in the line.

As thus far described, the apparatus of Figs. 6, 7, 8

and 9 have furnished gating pulses to the tive gate cir-v cuits together with live different phases of the subcarrier frequency wave from oscillator 136. As has been stated, the output or load circuits of all of the gates are joined to a common lead 132 which ends with terminal 13251. Connected between lead 132 which is common to the ve gate circuits loads and to a source of positive operating potential indicated as +260 volts is a lter circuit 74 in the form of a peaking arrangement which in cludes inductance 74a and capacitance 74h. The peaking circuit serves as a bandpass ilter Whose lower and upper cutot points may be, for example, two and live megacycles, respectively. In other words, the bandpass' filter 74 is centered on the subcarrier wave frequency of approximately 3.58 megacycles. This filter is included for the purpose of eliminating unwanted disturbances resulting from the gating action inthe ve gating tubes.

Terminal 132a is actually connected to the input terminal 132b of Fig. l() wherein is shown a mixer or adder stage 76 comprising a dual triode 162 whose two sections are connected in the manner illustrated. Coupled via capacitor 164 to the control grid of the right hand section of adder tube 162 are the successive bursts from the ve gate tubes. Also shown in Fig. 10 is a sync pulse ampliiier 166 which is of conventional design and which has applied to its control grid, via terminals H (Fig. 6) and H, the positive-going sync pulses from the output of oscillator 34. The amplied sync pulses are coupled via capacitor 168 to the control grid of the left hand section of adder tube 162. Thus, the composite output of tube 162 when viewed at terminal 170 will be substantially identical to the waveform ofrFig. 5, with the exception that its polarity will be the reverse thereof. The

Y output of adder tube 162, including sync pulses and bursts, is applied via capacitor 172 to the input of output amplifier 78 which is also conventional as to circuitry and which need not be described in detail. The linal output of the apparatus is available at terminal 80 in Fig. 10 and is a replica of the waveform of Fig. 5.

Fig. 11 is a vector diagram illustrating the relationships of the ve subcarrier frequency bursts. By comparing Fig. 1l with thepvector diagram of Fig. l it may be noted that each test burst is exactly 90 out of phase with the phase position of the corresponding signal component, and that the same burst that provides a test for R-Y is in the correct phase to serve as a color synchronizing burst. Since the demodulation process performed by demodulators 20 and 21 of the receiver of Fig. 2 is that of multiplication, the result of the rotation will be that of providing zero output at each circuit in the receiver for the burst which is designated by the term which each such circuit normally provides in normal operation. That is to say, therefore, in normal operation of the receiver, the I demodulator 21 is fed a continuous wave from the oscillator 15, which wave is in exact phase with the l signal transmitted by the broadcast station. Hence, in such normal broadcast operation, the I demodulator 2t) willl provide maximum output when I signal is present. Similarly (in broadcast operation) the Q demodulator is provided with a continuous subcarrier frequency wave whose phase is identical to that of the transmitted Q signal, so that its output is maximum when Q signal is present.

By applying the test signal of Fig. 5 (the angular relationships of which are shown by the vector diagram of Fig. 11) to the video amplilier of the receiver of Fig. 2 with the 90 phase shift of the so-called 1, Q and color difference signal bursts, the alignment of the receiver may be determined by connecting the vertical deflecting plates of a cathode ray oscilloscope to each of the following points, and observing the resultant Waveorms, which are illustrated by Fig. 12(a) and Fig. 12(b):

(l) At the output of low pass filter 23 in the Q channel as shown in Fig. 12(1)) the signal level correspending-to the burst in the test waveform designated Q will be of zero amplitude while the signal level corresponding to each of the other bursts will have some amplitude. If the horizontal sweep of the cathode ray oscilloscope is synchronized at any odd multiple of the line frequency, the waveforms corresponding to lines No. 1 and No. 2 are superimposed, and the no-burst interval of line No. 2 provides Va convenient zero reference line'in the pattern.

v(2,) At the output of the low pass -iilter 24 in the I channel (as in Fig. 12(a)) the signal level corresponding to the I burst in the test waveform will have zero am-v plitude while each of the other four will have some amplitude.

In addition to testing the phase alignment of the I and Q demodulators, the test signal produced by the apparatus of Figs. 6 1() is equally effective in testing theadjustment of the matrixing circuits of a color receiver. This latter utility may also be understood from a comparison of the vector diagrams of Figs. 1 and 11 which illustrate the fact that the test bursts designated (iR-Y), (G-Y) and (B-Y) are displaced 90 from the normal angular positions at which those signals are located in broadcast. Because of the phase shift employed, the matrixing circuit will produce a zero output, respectively, for each of the color difference designated bursts at the terminals at which signals of corresponding color normally appear. In order to test the alignment of the matrix of a color television receiver, therefore, it is necessary only to connect the vertical detlecting plates of an oscilloscope across each of the following terminals and observe the burst envelopes:

(1) At the red signal electrode of the color kinescope, the signal level corresponding to the burst designated (R-Y) in Fig. 5 will be zero while the other burst intervals are of various amplitudes;

(2) At the green signal electrode of the kinescope, the interval of only the (G-Y)- burst will be zero; and

(3) At the blue signal electrode of the kinescope, only the (B-Y) burst interval will have zero amplitude.

At this point, it should be noted that the reason for eliminating the last four bursts from alternate television lines in the test signal is to provide an unmodulated sweep ofthe oscilloscope used in the test. That is, the scanning electron beam is permitted, during alternate line intervals, to sweep across the phosphor screen along a zero i wir amplitudeline whereby to produce a convenient reference line on the oscilloscope screen for use in observing the signal amplitudes during the various burst intervals "on succeedinglines. This zero reference line `does not-extend ithrough the iirst burst interval, because "that-burst is present on every line.

Inview'of the foregoing explanation, it Should be apparent to those skilled in the art that thetest signal Waveform generatedby the apparatus of the present invention alords a ready indication of the phase alignmentof the I and Q demodulators of a color television receiver. Assumingthat the fI and Q test signalsiare notzero at the output terminalsof the I and Q'demodu1ators, respectively, thel phasing of the demodulators can be varied until the zero outputs are observed. Additionally, by checking the phasing of the demodulators at the outset, the later observations at the .color Ysignal felectrodes of the kinescope are direct indicationsofthecondition of thematrixing circuits, whichis extremelyhelpful 'in the servicing or original alignment'of'receivers;

VStillI- another use to which the test signalk described supra may be put is Vthat of checking the .gains of the 'various color or chrominance channels with respect to the gain of the'luminance channel. This test may beconducted simultaneously with the test of vthe matrixing circuits, since it involves the observation,-on'an oscilloscope, of' burst envelope levels at the several color'signal electrodes of the receiver under consideration. vMore specilically, the gain ofeach of the color channels relative'to luminance gain may be determined by examining the test waveform at each of the following p-oints in the color kinescope:

(1) On the blue signal electrode, the rst burst level (R-Y) should be substantially .equal in amplitude :.to'the sync pulse level when the .gain of` the blue channel in the receiver is correctly set. While thereason :forthis fact maybe shown by .use of the equations vof Fig. l, a simpler explanation is that, because of the 90 difference betweenthe bursts of Fig. 11 and the standard vector positions of Fig. 1, the (R-Y) burst. actually constitutes' a blue color difference Signal, insofar as the receiver is concerned. Accordingto the Equation 8 of Fig. 2, the gain of (B-Y) channel should properly be 2.03 relative to the gain of the Y channel in order for the receiver to derive the blue color diierence signal from the I and Q proportions shown. If the peakto-peak amplitude of the test bursts is made equal to the amplitude of the sync pulse (which may be considered unity), then the peak amplitude is 0.5. In a correctly adjusted (B-Y) channel, this peak signal is multiplied by 2.03, yielding an output level that is substantially, although not exactly, equal to unity, which means that the (R-Y) burst envelope will be apparently equal to sync pulse amplitude (and of the same polarity) when the blue channel gain is correct.

(2) On the green signal electrode of the kinescope, the level of the signal during the last or (B-Y) burst should be equal to 29 percent of the sync pulse amplitude and of the same polarity. The reason for this relationship stems, rst of all, from the fact that the (B-Y) test burst is actually an (R-Y) signal, in view of the 90 rotation of the vectors. By measuring the projection of the (B-Y) test burst of Fig. 1l into the (G-Y) phase direction as shown in Fig. 1, it may be seen that the projection (i. e., the length of (G-Y) from its origin to a perpendicular drawn from the extremity of the (B-Y) test burst vector to the (G-Y) vector) is proportional to the cosine of the angle between (R-Y) and (G-Y), or 34.3 which is equal to 0.825. Since the proper gain of the (G-Y) channel is 0.703 from Equation 9 in Fig. l, the projection of a test burst of 0.5 peak amplitude is proportional to 0.5 .825 .703 or 0.29. Consequently, the correct amplitude during the (B-Y) test burst interval in the (G--Y) channel is equal to 0.29, or 29 percent of sync amplitude, which is unity.

(3) On the red signalhelectrode of the kinescope, the envelope of the I burst should be equal tosubstantially 31 percent of the-sync-pulse amplitude and ofthe same polarity, assuming rthe gain of the red channelisproperly set. It is necessary, in illustrating the derivation of the value 31 percent, to measure the projection lofthe .I test burst vector of Fig. ll into the (R-Y) phase direction, as shown in Fig. 1. These twovectors dene va'nangle of 57 whose cosine is 0.545. Since the;gai n of the ;(R-Y) channel must be 1.14 (Equation ,7), Vthe signal level produced in the red channel byan I test burst of 0.5 peak amplitude is equal to0.5 0.5745 1.14 or 0531 relative tothe sync pulses.

lIn each of the'above cases `of checking color gain, the -gain control ofthe circuit in question may-be varied,fif necessary, to produce the desired demodulated burst level with respectto the level of the sync pulse Which-level is, as explained, 'a' true indication of correct color gain.

While it has notbeen speciiicallypointed out hereinabove, the horizontalsweep circuits. of the cathode'ray oscilloscope employed in making the observations enumerated supra may be conveniently synchronized with the test signal generator of thepresent invention byconnecting the sweep circuits to the sync output'terminal 82 v(Figs. 4 -and 6) thereby to use the sync pulses -36 for such purpose.

'From the foregoing, it will be recognized that the apparatus of the present invention provides a test signal Waveform each of whose component signals serves -the ends of determining the phase and gain alignments vand settings in a color television receiver of the'type described. Although the invention has been described in accordance with a specilic embodiment vwhereinthe'various elements, including delay lines, havebeen selected to produce a signal matched in a particular manner "tothe proposed NTSC standards, it shouldbe borne in mind. that the ldiiferent. burst phases may 'be'changed, as'may the oscillator frequency, to lit different standards. Moreover,the fact that specific forms of multivibrators, gate circuits Vand the like havebeendisclosed'by way ofillustration of an operative embodiment Ashould not be construed as by way ofli'mitation, since changes may be made Atherein without departing from the scope of the invention as dened by the appended claims.

Having thus described my invention, what I claim as new and desire to secure by Letters Patent is:

1. A test signal generator for color television receiver apparatus of the type adapted to derive component color signals from received color information in lthe form of a color carrier wave whose separate phases are modulated in accordance with color difference signals, which comprises: a source of sinusoidal oscillation of frequency substantially equal to the frequency of such color carrier wave; means for deriving separate phases of such oscillations, each bearing a predetermined relation to such separate phases of such color carrier wave; a source of television line rate synchronizing pulses; and means responsive to such synchronizing pulses for producing sequentially, within a television line interval, a burst of each of such separate phases of sinusoidal oscillation and means for adding such synchronizing pulses to such bursts, each Vof said produced bursts being displaced in phase by from a corresponding one of said separate phases of said color carrier Wave.

2. The invention as defined in claim 1 wherein said last-named means includes means for eliminating all except the lirst one of such bursts during predetermined line intervals.

3. A test signal generator for color television receiver apparatus of the type adapted to derive component color signals from received color television information in the form of a plurality of phases of a color carrier wave,` each phase being modulated in accordance with selected chrominance-representative signals, which comprises: oscillator means for producing a sinusoidal wave equal in assess? A s frequency tothe frequency of such color carrier Wave, means for deriving a plurality of separate phases of such sinusoidal wave, each phase bearing a fixed angular relationship to one of such plurality of color carrier wave,

phases; and gating means coupled to said last-named means for producing sequentially, within a television line interval, a burst of each of such separate phases of sinusoidal oscillation.

4. The invention as dened by claim 3 wherein said gating means comprises normally open electronic switch for each of such separate phases of sinusoidal oscillation and means for successively closing said switches.

5. The invention as defined by claim 3 wherein said gating means comprises an electronic switch for each of such separate phases of sinusoidal oscillation, a source of television line synchronizing pulses, and means responsive to such pulses for closing said switches successively.

6. The invention as defined by claim 5 wherein lsaid last-named means comprises a multivibrator coupled to each of said switches and to each other and means for applying such synchronizing pulses to one of said multivibrators.

7. A test signal generator for color television receiver apparatus of the type adapted to derive component color signals from received color television information in the form of a first phase of a color carrier wave modulated by a rst set of chrominance signals and a second phase of such carrier wave displaced from said rst phase by a xed angle modulated by a second set of chrominance signals, which comprises: an oscillator for producing a wave of sinusoidal energy of frequency substantially equal to the frequency of such color carrier wave; a source of television line rate synchronizing pulses; means coupled to said oscillator for shifting the phase of such sinusoidal wave; and means responsive tosynchronizing pulses from said source for sequentially producing, within a television line interval, a rst burst of sinusoidal energy of said frequency and of substantially the same phase as one of said color carrier wave phases and a second burst of sinusoidal Venergy of said frequency, the phase of said second burst being angularly displaced from the phase of said first burst by an amount equal to the angular dis- 16 placement between such first and second color carrier wave phases.

8. A test signal generator for color television receiver apparatus of the type having means for deriving component color signals from received color television information in the form of two phases of a color carrier wave of fixed frequency separated in phase by a xed angle, each phase being the vectorial resultant of a plurality of color difference signals, each of which is represented by a vector having a predetermined phase with respect t0 a reference which comprises: an oscillator for producing a wave of sinusoidal energy of such fixed frequency; a source of television line rate synchronizing pulses; means coupled to said oscillator for shifting the phase of such sinusoidal wave; and means coupled to said last-named means and responsive to such synchronizing pulses for producing sequentially, within a television line interval, a first burst of sinusoidal energy of said fixed frequency and of substantially the same phase as one of such carrier wave phases, a second burst of such energy whose phase is displaced from the phase of such first burst by an angle substantially equal to such xed angle, and a plurality of additional bursts each of which has a phase corresponding to that of one of such color difference signal vectors.

9. The invention as defined by claim 8 wherein said phase-shifting means comprises a length of delay line and wherein said last-named means comprises a plurality of gates connected to spaced points on said delay line and means for rendering said gates conductive in succession.

References Cited in the tile of this patent UNITED STATES PATENTS 2,666,181 Courtillot Ian. 12, 1954 2,733,433 Morrison Jan. 31, 1956 2,734,939 Houghton Feb. 14, 1956 2,736,761 Sziklai Feb. 28, 1956 OTHER REFERENCES Principles of NTSC Compatible Color Television, pp. 88-97, Electronics, February 1952. 

